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ts6001 page 1 ? 2014 silicon laboratories, inc. all rights reserved. features ? improved electrical performance over max6025 ? initial accuracy: 0.08% (max) ? ts6001a 0.16% (max) ? ts6001b ? temperature coefficient: 7ppm/c (max) ? ts6001a 10ppm/c (max) ? ts6001b ? quiescent supply current: 35 a (max) ? low supply current change with v in : 0.1 a/v ? output source/sink current: 500a ? low dropout at 500 a load current: 75mv ? load regulation: 30ppm/ma ? line regulation: 10ppm/v ? stable with c load up to 2200pf applications battery-operated equipment data acquisition systems hand-held equipment smart industrial transmitters industrial and process-control systems precision 3v/5v systems hard-disk drives description the ts6001 is a 3-terminal, series-mode 2.5-v precision voltage reference and is a pin-for-pin, identical to the max6025 voltage reference with improved electrical performance. the ts6001 consumes only 31 a of supply current at no-load, exhibits an initial output vo ltage accuracy of less than 0.08%, and a low output voltage temperature coefficient of 7ppm/c. in addition, the ts6001?s output stage is stable for all capacitive loads to 2200pf and is capable of sinking and sourcing load currents up to 500a. since the ts6001 is a series-mode voltage reference, its supply current is not affected by changes in the applied supply voltage unlike two-terminal shunt- mode references that require an external resistor. the ts6001?s small form factor and low supply current operation all combine to make it an ideal choice in low-power, precision applications. the ts6001 is fully specified over the -40c to +85c temperature range and is available in a 3-pin sot23 package. a 7ppm/ c, 0.08% precision +2.5v voltage reference in sot23 typical application circuit temperature drift- c output voltage - volt -40 -15 10 35 85 60 2.4995 2.4990 three typical devices device #1 device #2 device #3 2.5005 2.5000 2.5010 output voltage temperature drift
ts6001 page 2 ts6001 rev. 1.0 absolute maximum ratings in to gnd ................................................................. -0.3v to +13.5v out to gnd .................................................................... -0.3v to 7v short circuit to gnd or in (v in < 6v) .............................. continuous output short circuit to gnd or in (v in 6v) .............................. 60s continuous power dissipation (t a = +70c) 3-pin sot23 (derate at 4.0mw/c above +70c) .......... 320mw operating temperature range ................................. -40c to +85c storage temperature range .................................. -65c to +150c lead temperature (soldering, 10s) ...................................... +300c electrical and thermal stresses beyond those listed under ?absolute maximum ratings? ma y cause permanent damage to the device. these are stress ratings only and functional operation of the device at these or any other condition beyond those indicated in the op erational sections of the specifications is not implied. ex posure to any absolute maximum rating conditions for extended periods may affect device reliability and lifetime. package/ordering information order number part marking carrierquantity ts6001aig325 aag tape & reel ----- ts6001aig325t tape & reel 3000 TS6001BIG325 aah tape & reel ----- TS6001BIG325t tape & reel 3000 lead-free program: silicon labs supplies only lead-free packaging. consult silicon labs for produ cts specified with wider oper ating temperature ranges.
ts6001 ts6001 rev. 1.0 page 3 electrical characteristics v in = +5v, i out = 0, t a = t min to t max , unless otherwise noted. typical values are at t a = +25c. see note 1. parameter symbol conditions min typ max units output output voltage v out t a = +25c ts6001a 2.498 2.500 2.502 v -0.08 0.08 % ts6001b 2.496 2.500 2.504 v -0.16 0.16 % output voltage temperature coefficient (see note 2) tcv out 0c t a +85c ts6001a 2 7 ppm/c -40c t a +85c 2.5 10 0c t a +85c ts6001b 3 10 -40c t a +85c 4 15 line regulation ( ? v out /v out ) /? v in (v out + 0.2v) v in 12.6v 10 30 ppm/v load regulation ( ? v out /v out ) /? i out sourcing 0 i out 500 a 30 240 ppm/ma sinking -500 a i out 0 70 320 dropout voltage (see note 3) v in -v out i out = 500 a 75 150 mv out short-circuit current i sc v out short to gnd 4 ma v out short to in 4 temperature hysteresis (see note 4) 100 ppm long-term stability (see note 5) ? v out / time 168hr at t a = +25c 75 ppm/ 168hr dynamic noise voltage e out f = 0.1hz to 10hz 50 v p-p f = 10hz to 10khz 75 v rms ripple rejection ? v out / ? v in v in = 5v 100mv, f = 120hz 82 db turn-on settling time t r to v out = 0.1% of final value, c out = 50 pf 340 s capacitive-load stability range c out see note 6 0 2200 pf input supply voltage range v in guaranteed by line-regulation test v out + 0.2 12.6 v quiescent supply current i in 31 35 a change in supply current i in /v in (v out + 0.2v) v in 12.6v 0.1 2 a/v note 1: all devices are 100% production tested at t a = +25c and are guaranteed by characterization for t a = t min to t max , as specified. note 2: temperature coefficient is measured by the ?box? method; i.e., the maximum ? v out is divided by the maximum ? t. note 3: dropout voltage is the minimum input voltage at which v out changes 0.2% from v out at v in = 5.0v. note 4: temperature hysteresis is defined as the change in the +25c output voltage before and after cycling the device from +25c to t min to +25c and from +25c to t max to +25c. note 5: reference long-term drift or stability listed in the table is an intermediate result of a 1000-hour evaluation. soldered onto a printed circuit board (pcb), voltage references exhibit more drift early in the evaluation bec ause of assembly-induced differential str esses between the package and the pcb. note 6: not production tested; guaranteed by design.
ts6001 page 4 ts6001 rev. 1.0 line regulation output voltage change - ppm supply voltage - volt -40 0 80 120 t a = -40c t a = +85c 40 load current- ma t a = +85 c load regulation -0.5 0.5 0.25 -0.25 -160 -80 160 0 80 source current- a dropout voltage - v dropout voltage vs source current 400 800 0 1000 600 200 0 0.1 0.4 0.2 0.3 time - hours output voltage change - ppm 0 t a = +25c t a = +85c t a = -40c 8 12 2 14 10 4 6 t a = -40c typical performance characteristics v in = +5v; i out = 0ma; t a = +25 c, unless otherwise noted. t a = +25c t a = +25 c three typical devices device #1 0 42 84 168 126 2.5050 output voltage - volt device #2 device #3 long-term output voltage drift temperature drift- c output voltage - volt -40 -15 10 35 85 60 2.4995 2.4990 three typical devices device #1 device #2 device #3 2.5005 2.5000 2.5010 output voltage temperature drift output voltage error - % number of units 0 0.02 2 0 7 6 9 output voltage histogram -0.02 0.04 4 8 5 3 1 2.5025 2.5000 2.4950 2.4975
ts6001 ts6001 rev. 1.0 page 5 power supply rejection vs frequency 0.1hz to 10hz output noise v out(n) 10v/div output impedance - ? frequency - hz 1 10 1k 0.1 100 10k 0.1 1 100 1m 10k 1s/div 200s/div power-on transient response input 2v/div supply current vs input voltage supply curent - a input voltage - volt 20 28 36 40 8 12 2 14 32 10 supply current vs temperature temperature - c supply curent - a v cc = +2.5v, +5.5v v cc =+12.5v -40 -15 10 35 85 60 25 35 20 30 40 output impedance vs frequency output 1v/div v cc =+7.5v 4 6 24 typical performance characteristics v in = +5v; i out = 0ma; t a = +25 c, unless otherwise noted. 46v pp power supply rejection ? mv/v frequency - hz v cc =+5.5v0.25v 1 10 0.01 100 100 1k 10k 1m 100k 0.1
ts6001 page 6 ts6001 rev. 1.0 line transient response 2s/div 10s/div i out 1ma/div output 200mv/div v in =5v0.25v, ac-coupled v in 200mv/div output 100mv/div large-signal load transient response i out = 0ma 1ma 0ma, ac-coupled 10s/div small-signal load transient response i out 50a/div output 20mv/div i out = 0a 50a 0a, ac-coupled typical performance characteristics v in = +5v; i out = 0ma; t a = +25 c, unless otherwise noted.
ts6001 ts6001 rev. 1.0 page 7 pin functions pin name function 1 in supply voltage input 2 out +2.5v output 3 gnd ground description/theory of operation the ts6001 incorporates a precision 1.25-v bandgap reference that is followed by an output amplifier configured to amplify the base bandgap output voltage to a 2.5-v output. the design of the bandgap reference incorporates proprietary circuit design techniques to achieve its low temperature coefficient of 7ppm/c and initial output voltage accuracy less than 0.08%. the design of the output amplifier?s frequency compensation does not require a separate compensation capacitor and is stable with capacitive loads up to 2200pf. the design of the output amplifier also incorporates low headroom design as it can source and sink load currents to 500 a with a dropout voltage less than 100mv. applications information power supply input bypass capacitance if there are other analog ics within 1 to 2 inches of the ts6001 with their own bypass capacitors to gnd, the ts6001 would not then require its own bypass capacitor. if this is not the case, then it is considered good analog circuit engineering practice to place a 0.1f ceramic capacitor in as close proximity to the ts6001 as practical with very short pcb track lengths. output/load capacitance considerations as mentioned previously, the ts6001 does not require a separate, external capacitor at v out for transient response stability as it is stable for capacitive loads up to 2200pf. for improved load regulation transient response, the use of a capacitor at v out helps to reduce output voltage overshoot/undershoot to transient load current conditions. figure 1 illustrates the ts6001?s transient load regulation performance with c load = 0pf to a 50-a transient upon a 175-a steady-state load current. peak transients are approximately 20mv and the ts6001 settles in less than 8s. as shown in figure 2, adding a capacitive load reduces peak transients at the expense of settling time. in this case, the ts6001?s output was loaded with c load = 1000pf and subjected to the same transient load current profile. peak transients were reduced to less than 10mv and the ts6001 settled in less than 10s. figure 2: ts6001 transient load regulation response, c load = 1000pf i out 50a/div output 20mv/div i out = 175a 225a 175a figure 1: ts6001 transient load regulation response, c load = 0pf i out = 175a 225a 175a i out 50a/div output 20mv/div
ts6001 page 8 ts6001 rev. 1.0 supply current the ts6001 exhibits excellent dc line regulation as its supply current changes slightly as a function of the applied supply voltage. be cause of a unique bias loop design, the change in its supply current as a function of supply voltage (its ? i in / ? v in ) is less than 0.1 a/v. since the ts6001 is a series-mode reference, load current is drawn from the supply voltage only when required. in this case, circuit efficiency is maintained at all applied supply voltages. reducing power dissipation and extending battery life are the net benefits of improved circuit efficiency. when the applied supply voltage is less than the minimum specified input voltage of the ts6001 (for example, during the pow er-up or ?cold-start? transition), the ts6001 performs an internal calibration routine and can draw up to 200 a above its nominal, steady-state supply current. this internal calibration sequence also dominates the ts6001?s turn-on time. to ensure reliable power-up behavior, the input power source must have sufficient reserve power to provide the extra supply current drawn during the power-up transition. voltage reference turn-on time with a (v in ? v out ) voltage differential larger than 200mv and i load = 0ma, the ts6001?s typical combined turn-on and settling time to within 0.1% of its 2.5v final value is approximately 340 s. output voltage hysteresis reference output voltage thermal hysteresis is the change in the reference?s +25c output voltage after temperature cycling from +25c to +85c to +25c and from +25c to -40c to +25c. thermal hysteresis is caused by differential package stress impressed upon the ts6001?s internal bandgap core transistors and depends on whether the reference ic was previously at a higher or lower temperature. at 100ppm, the ts6001?s typical temperature hysteresis is equal to 0.25mv with respect to a 2.5v output voltage. connecting two or more ts6001s in stacked v out arrangements in many applications, it is desired to combine the outputs of two or more precision voltage references, especially if the combined output voltage is not available or is an uncommon output voltage. one such technique for combining (or ?stacking?) the outputs of precision voltage references is illustrated in figure 3. in this example and powered by an unregulated supply voltage (v in +5.2v), two ts6001-2.5 precision voltage references are used. the gnd terminal of refa is connected to the out terminal of refb. this connection produces two output voltages, v refout1 and v refout2 , where v refout1 is the terminal voltage of refb and v refout2 is v refout1 plus the out terminal voltage of refb. by implementing this stacked arrangement with a pair of ts6001-2.5s, v refout2 is 5v and v refout1 is 2.5v. although the ts6001-2.5s do not specifically require input bypass capacitors, it is good engineering practice to bypass both references from v in to the global gnd terminal (at refb). if either or both reference ics are required to drive a load capacitance, it is also good engineering practice to route the load capacitor?s return lead to each reference?s corresponding ref?s gnd terminal. the circuit?s minimum input supply voltage, v in , is determined by v refout2 and refb?s dropout voltage (75mv, typically). how to configure the ts6001 into a general- purpose current source in many low-voltage applications, a general-purpose current source is needed with very good line regulation. the ts6001-2.5 can be configured as a grounded-load, floating current source as shown figure 4. in this exampl e, the ts6001-2.5?s output voltage is bootstrapped across an external resistor (r1 + p1) which, in turn, sets the output current. the circuit?s total output current is i out = i set +i qsc where i qsc is the ts6001 supply current (up to 35a). for figure 3: connecting two ts6001-2.5s in a stacked v refout arrangement
ts6001 ts6001 rev. 1.0 page 9 improved output current accuracy, i set should be at least 10 times i qsc . a negative, precision voltage reference without precision resistors when using current-output dacs, it is oftentimes desired that the polarity of the output signal voltage is the same as the external reference voltage. there are two conventional techniques used to accomplish this objective: a) inverting the full-scale dac output voltage or b) converting a current-output dac into a voltage-switching dac. in the first technique, an op amp and pair of precision resistors would be required because the dac?s output signal voltage requires re-inversion to match the polarity of the external reference voltage. the second technique is a bit more involved and requires converting the current-output dac into a voltage-switching dac by driving the dac?s vref and iout terminals in reverse. additional components required are two precision resistors, an op amp, and an external voltage reference, typically a 1.25-v reference. if the 1.25-v full-scale output voltage requires scaling to a 2.5-v or a 5-v full scale, then a second op amp and pair of precision resistor s would be necessary to perform the amplification. to avoid the need for eit her re-inversion of the current-switching dac?s output voltage or amplifying the voltage-switching dac?s output voltage, it would then be desired to apply a negative voltage reference to the original current-switching dac. in general, any positive voltage reference can be converted into a negative voltage reference using pair of matched resistors and an op amp configured for inverting mode operation. the disadvantage to this approach is that the largest single source of error in the circuit is the relative matching of the resistors used. the circuit illustrated in fi gure 5 avoids the need for multiple op amps and well-matched resistors by using an active integrator ci rcuit. in this circuit, the voltage reference?s output is used as the input signal to the integrator. because of op amp loop action, the integrator adjusts its output voltage to establish the correct relationship between the reference?s out and gnd terminals (=v ref ). in other words, the output voltage polarity of t he integrator stage is opposite that of the reference?s output voltage. the 2200pf capacitor at t he output of the ts6001 is optional and the resistor in series with the output of the op amp should be empirically determined based on the amplifier choice and whether the amplifier is required to drive a large capacitive load. rail-to-rail output op amps used for the integrator stage work best in this application; however, these types of op amps require a finite amount of headroom (in the millivolt range) when sinking load current. therefore, good engineering judgment is always recommended when selecting the most appropriate negative suppl y for the circuit. how to use the ts6001 in a high-input voltage floating current source by adopting the technique previously shown in figure 2, the basic floating current source circuit can be adapted to operate at much higher supply voltages beyond the supply voltage rating of the ts6001-2.5 by adding a discrete n-channel jfet. as shown in figure 6, the jfet acts as a supply voltage regulator since its so urce voltage will always be 2.5v higher than v sy . the circuit minimizes reference ic self-heating because the jfet and the 2n3904 npn transistor carry the load current. this circuit can operate up to +35v and is determined by the bv ds breakdown voltage of the external jfet. figure 4: a low-power, general-purpose current source. figure 5: how to convert a v ref to a ?v ref without precision resistors.
ts6001 page 10 ts6001 rev. 1.0 for example, if v sy is 0v, then the upper input supply voltage level for the circuit is 35v. with a 2.1k ? load and the ts6001?s supply current of 35a (max), this circuit supplies approximately a 1.23-ma current to the load. in many current source a pplications, the possibility of an output short-circuit condition - whether transient or sustained - exists. it is recommended to test thoroughly for either scenario to prevent the possibility that the ts600 1 would be exposed to a total voltage from its in terminal to gnd terminal higher than its absolute maximum rating of 13.5v. boosting the ts6001?s output current drive while the ts6001 is capable of sourcing up to 500a with excellent load regulation, there are applications where tight load regulation is required at much higher output load currents. by adding a general-purpose, industry-standard pnp transistor and one resistor to the ts6001?s basic configuration as shown in figure 7, increasing a precision reference?s output source current drive is straightforward. using a 2n2905 pnp transistor and a 1.5k ? resistor, the ts6001 is able to maintain excellent load regulation while sourcing load currents up to 150ma. if the application circuit is designed to operate across a wide temperature range, it is recommended that circuit performance is thoroughly evaluated across the pnp transistor?s beta ( , or current gain) distribution. when the pnp transistor?s current gain is a minimum, the increase in base current must be absorbed by the ts6001 for a given load current. for higher output load currents, higher output power pnp transistors can be used so long as good thermal management techniques are applied and transistor current-gain vs ambient temperature behavior is evaluated. figure 6: using the ts6001-2.5 in a high-input voltage floating current source. figure 7: boosting the ts6001?s output current with an external pnp transistor.
ts6001 ts6001 rev. 1.0 page 11 generating positive and negative low-power voltage references the circuit in figure 8 uses a cd4049 hex inverter and a few external capacitors as the power supply to a dual-supply precision op amp to form a 2.5v precision, bipolar output voltage reference around the ts6001. the cd4049-based circuit is a discrete charge pump voltage doubler/inverter that generates 6v supplies for any precision, micropower op amp with v os and tcv os specifications consistent with the ts6001?s initial accuracy and output voltage drift performance. figure 8: generating positive and negative 2.5v references from a single +3v or +5v supply.
ts6001 page 12 silicon laboratories, inc. ts6001 rev. 1.0 400 west cesar chavez, austin, tx 78701 +1 (512) 416-8500 ? www.silabs.com package outline drawing 3-pin sot23 package outline drawing (n.b., drawings are not to scale) patent notice silicon labs invests in research and development to help our custom ers differentiate in the market with innovative low-power, s mall size, analog-intensive mixed-signal solutions. s ilicon labs' extensive patent portfolio is a testament to our unique approach and wor ld-class engineering team. the information in this document is believed to be accurate in all respects at the time of publication but is subject to change without notice. silicon laboratories assumes no responsibility for errors and om issions, and disclaims responsib ility for any consequences resu lting from the use of information included herein. additionally, silicon laborat ories assumes no responsibility for the functioning of undescr ibed features or parameters. silicon laboratories reserves the right to make c hanges without further notice. silicon laboratories makes no warra nty, representation or guarantee regarding the suitability of its pr oducts for any particular purpose, nor does silicon laboratories assume any liability arising out of the application or use of any product or circ uit, and specifically disclaims any and all liability, in cluding without limitation consequential or incidental damages. silicon laboratories products are not designed, intended, or authorized for use in applica tions intended to support or sustain life, or for any other application in wh ich the failure of the silicon laboratories product could create a situation where personal injury or death may occur. should buyer purchase or use silicon laboratories products for any such unintended or unaut horized application, buyer shall indemnify and hold silicon laboratories harmless against all claims and damages. silicon laboratories and silicon labs are tr ademarks of silicon laboratories inc. other products or brandnames mentioned herein are trademarks or registered trademarks of their respective holders.
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